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1 ? fn7385.4 el5152, el5153, el5252, el5455 270mhz ultra-accurate amplifiers the el5152, el5153, el5252, and el5455 are 270mhz bandwidth -3db voltage mode feedback amplifiers with dc accuracy of <0.01%, 1mv offsets and 50kv/v open loop gains. these amplifiers are i deally suited for applications ranging from precision meas urement instrumentation to high-speed video and monitor applications demanding higher linearity at higher frequency. capable of operating with as little as 3.0ma of curr ent from a single supply ranging from 5v to 12v dual supplies ranging from 2.5v to 5.0v these amplifiers are also well suited for handheld, portable and battery-powered equipment. single amplifiers are offered in sot-23 packages and duals in a 10 ld msop package for applications where board space is critical. quad amplifiers are available in a 14 ld so package. additionally, singles and duals are available in the industry-standard 8 ld so. all parts operate over the industrial temperature range of -40c to +85c. features ? 270mhz -3db bandwidth ? 180v/s slew rate ? 1mv maximum v os ? very high open loop gains 50kv/v ? low supply current = 3ma ? 105ma output current ? single supplies from 5v to 12v ? dual supplies from 2.5v to 5v ? fast disable on the el5152 and el5252 ?low cost ? pb-free plus anneal available (rohs compliant) applications ?imaging ? instrumentation ?video ? communications devices pinouts el5152 (8 ld so) top view el5153 (5 ld sot-23) top view el5252 (10 ld msop) top view el5455 (14 ld so) top view 1 2 3 4 8 7 6 5 - + nc in- in+ vs- ce vs+ out nc 1 2 3 5 4 - + out vs- in+ vs+ in- 1 2 3 4 10 9 8 7 5 6 - + - + ina+ cea vs- ceb ina- outa vs+ outb inb+ inb- outa ina- ina+ vs+ outd ind- ind+ vs- inb+ inc+ 1 2 3 4 14 13 12 11 5 6 7 10 9 8 inc- outc inb- outb -+ - + -+ - + data sheet october 3, 2005 caution: these devices are sensitive to electrosta tic discharge; follow proper ic handling procedures. 1-888-intersil or 1-888-468-3774 | intersil (and design) is a registered trademark of intersil americas inc. copyright intersil americas inc. 2004, 2005. all rights reserved all other trademarks mentioned are the property of their respective owners.
2 fn7385.4 october 3, 2005 ordering information part number part marking tape & reel package pkg. dwg. # el5152is 5152is - 8 ld so mdp0027 el5152is-t7 5152is 7? 8 ld so mdp0027 el5152is-t13 5152is 13? 8 ld so mdp0027 el5152isz (see note) 5152isz - 8 ld so (pb-free) mdp0027 el5152isz-t7 (see note) 5152isz 7? 8 ld so (pb-free) mdp0027 el5152isz-t13 (see note) 5152isz 13? 8 ld so (pb-free) mdp0027 el5153iw-t7 bgaa 7? (3k pcs) 5 ld sot-23 mdp0038 el5153iw-t7a bgaa 7? (250 pcs) 5 ld sot-23 mdp0038 el5153iwz-t7 (see note) baal 7? (3k pcs) 5 ld sot-23 (pb-free) mdp0038 el5153iwz-t7a (see note) baal 7? (250 pcs) 5 ld sot-23 (pb-free) mdp0038 el5252iy bagaa - 10 ld msop mdp0043 el5252iy-t7 bagaa 7? 10 ld msop mdp0043 el5252iy-t13 bagaa 13? 10 ld msop mdp0043 el5455is 5455is - 14 ld so mdp0027 el5455is-t7 5455is 7? 14 ld so mdp0027 el5455is-t13 5455is 13? 14 ld so mdp0027 el5455isz (see note) 5455isz - 14 ld so (pb-free) mdp0027 el5455isz-t7 (see note) 5455isz 7? 14 ld so (pb-free) mdp0027 EL5455ISZ-T13 (see note) 5455isz 13? 14 ld so (pb-free) mdp0027 note: intersil pb-free plus anneal products employ special pb-free material sets; mo lding compounds/die attach materials and 100 % matte tin plate termination finish, which are rohs compliant and compatible with both snpb and pb-free soldering operations. intersil pb-free p roducts are msl classified at pb-free peak reflow temper atures that meet or exceed the pb-free requirements of ipc/jedec j std-020. el5152, el5153, el5252, el5455
3 fn7385.4 october 3, 2005 absolute maxi mum ratings (t a = 25c) supply voltage between v s and gnd. . . . . . . . . . . . . . . . . . . 13.2v maximum continuous output current . . . . . . . . . . . . . . . . . . . 50ma pin voltages . . . . . . . . . . . . . . . . . . . . . . . . . gnd -0.5v to v s +0.5v power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . see curves junction temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +125c storage temperature . . . . . . . . . . . . . . . . . . . . . . . .-65c to +150c ambient operating temperature . . . . . . . . . . . . . . . .-40c to +85c current into i n +, i n -, ce . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5ma caution: stresses above those listed in ?absolute maximum ratings? may cause permanent damage to the device. this is a stress o nly rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. important note: all parameters having min/max specifications are guaranteed. typical values are for information purposes only. u nless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: t j = t c = t a electrical specifications v s + = +5v, v s - = 5v, r f = r g = 750 ? , r l = 150 ? , t a = 25c, unless otherwise specified. parameter description conditions min typ max unit ac performance bw -3db bandwidth a v = +1, r l = 500 ?, c l = 5.0pf 270 mhz a v = +2, r l = 150 ? 85 mhz gbwp gain bandwidth product r l = 150 ? 165 mhz bw1 0.1db bandwidth a v = +1, r l = 500 ? 50 mhz sr slew rate v o = -3v to +3v, a v = +2 120 155 v/s v o = -3v to +3v, a v = 1, r l = 500 ? 180 v/s t s 0.1% settling time v out = -1v to +1v, a v = +2 30 ns dg differential gain error a v = +2, r l = 150 ? 0.06 % dp differential phase error a v = +2, r l = 150 ? 0.045 v n input referred voltage noise 12 nv/ hz i n input referred current noise 1.8 pa/ hz dc performance v os offset voltage -1 0.5 1 mv t c v os input offset voltage temperature coefficient measured from t min to t max -2 v/c a vol open loop gain v o is from -2.5v to 2.5v (el5152 & el5153) 10 20 kv/v v o is from -2.5v to 2.5v (el5252 & el5455) 15 50 kv/v input characteristics cmir common mode input range guaranteed by cmrr test -2.5 2.5 v cmrr common mode rejection ratio v cm = 2.5 to -2.5 85 110 db i b bias current -0.4 0.12 +0.6 a i os input offset current -80 12 80 na r in input resistance 25 60 m ? c in input capacitance 1pf output characteristics v out output voltage swing r l = 150 ? to gnd 3.0 3.3 v r l = 500 ? to gnd 3.4 3.7 v i out output current r l = 10 ? to gnd 60 105 ma enable (selected packages only) t en enable time 200 ns t dis disable time 300 ns el5152, el5153, el5252, el5455
4 fn7385.4 october 3, 2005 i ihce ce pin input high current ce = v s +0-1a i ilce ce pin input low current ce = v s - 5 13 25 a v ihce ce input high voltage for power-down v s + -1 v v ilce ce input low voltage for power-up v s + -3 v supply i son supply current - enabled (per amplifier) no load, v in = 0v, ce = +5v 2.46 3.0 3.43 ma i soff supply current - disabled (per amplifier) no load, v in = 0v, ce = 5v 5 13 25 a psrr power supply rejection ratio dc, v s = 3.0v to 6.0v (el5152 & el5153) 85 116 db dc, v s = 3.0v to 6.0v (el5252 & el5455) 80 95 db electrical specifications v s + = +5v, v s - = 5v, r f = r g = 750 ? , r l = 150 ? , t a = 25c, unless otherwise specified. (continued) parameter description conditions min typ max unit typical performance curves figure 1. el5152 small signal frequency for various gains figure 2. el5152 small signal frequency phase for various gains figure 3. frequency response for various r l figure 4. frequency response for various c l normalized gain (db) 100k 1m 10m 500m frequency (hz) 100m supply=5.0v input=-30dbm=20mv r l =500 ? c l =5pf a v =+1 a v =+5 a v =+2 3 1 -1 -3 -5 4 2 0 -2 -4 -6 phase () 60 0 -60 -120 -180 90 30 -30 -90 -150 100k 1m 10m 500m frequency (hz) 100m supply=5.0v input=-30dbm=20mv r l =500 ? c l =5pf -210 a v =+5 a v =+2 a v =+1 normalized gain (db) 4 2 0 -2 -4 5 3 1 -1 -3 100k 1m 10m 500m frequency (hz) 100m c l =5pf a v =+1 10 ? 50 ? 150 ? 500 ? -5 normalized gain (db) 4 2 0 -2 -4 5 3 1 -1 -3 100k 1m 10m 500m frequency (hz) 100m a v =+1 r l =500 ? 10pf 12pf 4.7pf 3.3pf 2.2pf 1pf -5 what should label be fore this curve? el5152, el5153, el5252, el5455
5 fn7385.4 october 3, 2005 figure 5. frequency response for various r l figure 6. frequency response for various c l figure 7. frequency response for various r l figure 8. frequency response for various c l figure 9. frequency response for various c in figure 10. frequency response vs r f /r g typical performance curves (continued) normalized gain (db) 3 1 -1 -3 -5 4 2 0 -2 -4 100k 1m 10m 800m frequency (hz) 100m a v =+2 c l =5pf r f =500 ? 50 ? 100 ? 200 ? 250 ? 500 ? -6 normalized gain (db) 4 2 0 -2 -4 5 3 1 -1 -3 100k 1m 10m 500m frequency (hz) 100m a v =+2 r l =500 ? r f =500 ? 22pf 18pf 12pf 4.7pf 2.7pf -5 normalized gain (db) 3 1 -1 -3 -5 4 2 0 -2 -4 100k 1m 10m frequency (hz) 100m 50 ? 200 ? 500 ? 250 ? -6 a v =+5 c l =5pf r f =102 ? normalized gain (db) 3 1 -1 -3 -5 4 2 0 -2 -4 100k 1m 10m 500m frequency (hz) 100m r l =500 ? a v =+5 r f =102 ? 87pf 68pf 50pf 39pf 27pf 18pf -6 normalized gain (db) 4 2 0 -2 -4 5 3 1 -1 -3 100k 1m 10m 500m frequency (hz) 100m r l =150 ? a v =+2 r f =500 ? 4.7pf 3.3pf 3.2pf 1pf -5 normalized gain (db) 4 2 0 -2 -4 5 3 1 -1 -3 100k 1m 10m 500m frequency (hz) 100m r l =500 ? c l =5pf a v =+2 r f =r g = 1000 ? 1500 ? 750 ? 500 ? -5 el5152, el5153, el5252, el5455
6 fn7385.4 october 3, 2005 figure 11. frequency response for various c in figure 12. frequency response for various power supply figure 13. psrr figure 14. cmrr for various power supply values figure 15. output impedance figu re 16. enable/disable response typical performance curves (continued) normalized gain (db) -4 -2 0 -2 -4 -5 -3 -1 -1 -3 100k 1m 10m 300m frequency (hz) 100m r l =500 ? a v =+5 r f =102 ? -5 0pf 22pf 34pf normalized gain (db) 4 2 0 -2 -4 5 3 1 -1 -3 100k 1m 10m 500m frequency (hz) 100m supply=5.0v r l =500 ? a v =+2 r f =500 ? 2.0v 3.0v 4.0v 5.0v -5 10k 100k 100m frequency (hz) 1k 10m 1m -70 -60 -50 -40 -30 -20 -10 0 psrr (db) -80 -90 -100 a v =+1 cmrr (db) -40 -60 -80 -100 -120 -30 -50 -70 -90 -110 100 1k 100k 100m frequency (hz) 10k 10m 1m -130 2.5 3.0 5.0 1 0 k 1 0 0 k 1 0 0 m f r e q u e n c y ( h z ) 1 k 1 0 m 1 m 1 1 0 1 0 0 1 0 0 0 output impedance ( ? ) 0 . 0 1 0 . 0 0 1 a v = + 1 time (400ns/div) ch 2 ch 1 216ns enable 328ns disable a v =+1 r l =500 ? c l =0 el5152, el5153, el5252, el5455
7 fn7385.4 october 3, 2005 figure 17. rise time - large signal response f igure 18. fall time - large signal response figure 19. rise time - small signal response figure 20. fall time - small signal response figure 21. el5152 small signal open loop gain vs frequency inverting figure 22. el5252 small signal frequency vs crosstalk typical performance curves (continued) voltage (500mv/div) time (4ns/div) a v =+1 r l =500 ? c l =5pf 0v voltage (500mv/div) time (4ns/div) a v =+1 r l =500 ? c l =5pf 0v time (2ns/div) voltage (100mv/div) a v =+1 r l =500 ? c l =5pf 0v time (2ns/div) voltage (100mv/div) a v =+1 r l =500 ? c l =5pf 0v 1 0 k 1 0 0 k 1 0 0 m f r e q u e n c y ( h z ) 1 k 1 0 m 1 m g a i n ( d b ) p h a s e ( ) 5 0 0 m 80 60 40 20 0 90 70 50 30 10 -10 -45 0 45 90 135 180 gain phase crosstalk (db) -20 -40 -60 -80 -10 -30 -50 -70 -90 100k 1m 10m 1g frequency (hz) 100m a v =+1 r l -500 ? c l =0pf -100 in #2 out #1 in #1 out #2 el5152, el5153, el5252, el5455
8 fn7385.4 october 3, 2005 figure 23. supply current vs supply voltage figure 24. frequency response for various voltage supply levels figure 25. el5252 small signal frequency - channel to channel figure 26. package power dissipation vs ambient temperature figure 27. package power dissipation vs ambient temperature typical performance curves (continued) 0 2 3 4 5 6 7 1 1.5 2.5 3 3.5 4 4.5 5 voltage (v) supply current (ma) 2 1 a v =+2 r l =500 ? c l =5pf normalized gain (db) 3 1 -1 -3 -5 4 2 0 -2 -4 100k 1m 10m 800m frequency (hz) 100m r l =500 ? c l =0pf -6 2.0v 3.0v 4.0v 5.0v normalized gain (db) 4 2 0 -2 -4 5 3 1 -1 -3 100k 1m 10m 1g frequency (hz) 100m a v =+1 r l -500 ? c l =0pf -5 channel #1 channel #2 1.136w 909mw so14 ja =88c/w 1.4 1.2 1 0.8 0.6 0.2 0 0 255075100 150 ambient temperature (c) power dissipation (w) 125 85 jedec jesd51-7 high effective thermal conductivity test board 0.4 435mw 870mw 0.9 so8 ja =110c/w msop8/10 ja =115c/w sot23-5/6 ja =230c/w 833mw 625mw ja =160c/w so8 ja =120c/w so14 1 0.9 0.8 0.6 0.4 0.1 0 0 255075100 150 ambient temperature (c) power dissipation (w) 125 85 jedec jesd51-3 low effective thermal conductivity test board 0.2 0.7 0.3 0.5 391mw j a = 2 5 6 c / w s o t 2 3 - 5 / 6 486mw ja =206c/w msop8/10 el5152, el5153, el5252, el5455
9 fn7385.4 october 3, 2005 el5152 product description the el5152, el5153, el5252, and el5455 are wide bandwidth, low power, low offset voltage feedback operational amplifiers capable of operating from a single or dual power supplies. this family of operational amplifiers are internally compensated for closed loop gain of +1 or greater. connected in voltage follower mode, driving a 500 ? load members of this amplifier family demonstrate a -3db bandwidth of about 270mhz. with the loading set to accommodate typical video application, 150 ? load and gain set to +2, bandwidth reduces to about 180mhz with a 600v/s slew rate. power down pins on the el5152 and el5252 reduce the already low power demands of this amplifier family to 17a typical while the amplifier is disabled. input, output and supply voltage range the el5152 and el5153 families have been designed to operate with supply voltage ranging from 5v to 12v. supply voltages range from 2.5v to 5v for split supply operation. of course split supply oper ation can easily be achieved using single supplies by splitting off half of the single supply with a simple voltage divider as illustrated in the application circuit section. input common mode range these amplifiers have an input common mode voltage ranging from 1.5v above the negative supply (v s - pin) to 1.5v below the positive supply (v s + pin). if the input signal is driven beyond this range the output signal will exhibit distortion. maximum output swing & load resistance the outputs of the el5152 and el5153 families maximum output swing ranges from -4v to 4v for v s = 5v with a load resistance of 500 ? . naturally, as the load resistance becomes lower, the output swing lowers accordingly; for instance, if the load resistor is 150 ? , the output swing ranges from -3.5v to 3.5v. this response is a simple application of ohms law indicating a lower value resistance results in greater current demands of the amplifier. additionally, the load resistance affects the frequency response of this family as well as all operational amplifiers, as clearly indicated by the gain vs frequency for various rl curves clearly indicate. in the case of the frequency response reduced bandwidth with decreasing load resistance is a function of load resistance in conjunction with the output zero response of the amplifier. choosing a feedback resistor a feedback resistor is required to achieve unity gain; simply short the output pin to the inve rting input pin. gains greater than +1 require a feedback and gain resistor to set the desired gain. this gets interesting because the feedback resistor forms a pole with the parasitic capacitance at the inverting input. as the feedb ack resistance increases the position of the pole shifts in the frequency domain, the amplifier's phase margin is reduced and the amplifier becomes less stable. peaking in the frequency domain and ringing in the time domain are symptomatic of this shift in pole location. so we want to keep the feedback resistor as small as possible. you may want to use a large feedback resistor for some reason; in th is case to compensate the shift of the pole and maintain stability a small capacitor in the few pico farad range in parallel with the feedback resistor is recommended. for the gains greater than unity, it has been determined a feedback resistance ranging from 500 ? to 750 ? provides optimal response. gain bandwidth product the el5156 and el5157 families have a gain bandwidth product of 210mhz for a gain of +5. bandwidth can be predicted by the following equation: video performance for good video performance, an amplifier is required to maintain the same output impedance and same frequency response as dc levels are changed at the output; this characteristic is widely referred to as ?diffgain-diffphase?. many amplifiers have a difficult time with this especially while driving standard video loads of 150 ? , as the output current has a natural tendency to change with dc level. the el5152 dg and dp for these families is a respectable 0.006% and 0.04%, while driving 150 ? at a gain of 2. driving high impedance loads would give a similar or better dg and dp performance as the current output demands placed on the amplifier lessen with increased load. driving capacitive loads the el5152 and el5153 families can easily drive capacitive loads as demanding as 27pf in parallel with 500 ? while holding peaking to within 5db of peaking at unity gain. of course if less peaking is desired, a small series resistor (usually between 5 ? to 50 ? ) can be placed in series with the output to eliminate most peaking. however, there will be a small sacrifice of gain which can be recovered by simply adjusting the value of the gain resistor. driving cables both ends of all cables must always be properly terminated; double termination is absolutely necessary for reflection-free performance. additionally, a back-termination series resistor at the amplifier's output will is olate the amplifier from the cable and allow extensive capacitive drive. however, other applications may have high capacitive loads without a back- termination resistor. again, a small series resistor at the output can help to reduce peaking. gain bw gainba ndwidthproduct = el5152, el5153, el5252, el5455
10 fn7385.4 october 3, 2005 disable/power-down the el5152 and el5253 can be disabled with their output placed in a high impedance state. the turn off time is about 330ns and the turn on time is about 130ns. when disabled, the amplifier's supply current is reduced to 17a typically; essentially eliminating power consumption. the amplifier's power down is controlled by standard ttl or cmos signal levels at the enable pin. the applied logic signal is relative to v s - pin. letting the enable pin float or the application of a signal that is less than 0.8v above v s - enables the amplifier. the amplifier is disabled when the signal at enable pin is above v s + -1.5v. output drive capability the el5152 and el5153 families do not have internal short circuit protection circuitry. typically, short circuit currents as high as 95ma and 70ma can be expected and naturally, if the output is shorted indefini tely the part can easily be damaged from overheating, or excessive current density may eventually compromise metal integrity. maximum reliability is maintained if the output current is always held below 40ma. this limit is se t and limited by the design of the internal metal interconnect. note that in transient applications, the part is extremely robust. power dissipation with the high output drive capability of the el5152 and el5153 families, it is possible to exceed the 125c absolute maximum junction temperature under certain load current conditions. therefore, it is important to calculate the maximum junction temperature for an application to determine if load conditions or package types need to be modified to assure operation of the amplifier in a safe operating area. the maximum power dissipation allowed in a package is determined according to: where: t jmax = maximum junction temperature t amax = maximum ambi ent temperature ja = thermal resistance of the package the maximum power dissipation actually produced by an ic is the total quiescent supply current times the total power supply voltage, plus the power in the ic due to the load, or: for sourcing: for sinking: where: v s = supply voltage is max = maximum quiescent supply current v out = maximum output voltage of the application r load = load resistance tied to ground i load = load current n = number of amplifiers (max = 2) by setting the two pd max equations equal to each other, we can solve the output current and r load to avoid the device overheat. power supply bypassing printed circuit board layout as with any high frequency device, a good printed circuit board layout is necessary for optimum performance. lead lengths should be as short as possible. the power supply pin must be well bypassed to reduce the risk of oscillation. for normal single supply operation, where the v s - pin is connected to the ground plane, a single 4.7f tantalum capacitor in parallel with a 0. 1f ceramic capacitor from v s + to gnd will suffice. this same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. in this case, the v s - pin becomes the negative supply rail. see figure 1 for a complete tuned power supply bypass methodology. printed circuit board layout for good ac performance, parasitic capacitance should be kept to minimum. use of wire wound resistors should be avoided because of their additional series inductance. use of sockets should also be avoided if possible. sockets add parasitic inductance and capacitance that can result in compromised performance. minimizing parasitic capacitance at the amplifier's inverting in put pin is very important. the feedback resistor should be placed very close to the inverting input pin. strip line design techniques are recommended for the signal traces. pd max t jmax t amax ? ja -------------------------------------------- - = pd max v s i smax v s v outi ? () i1 = n v outi r li ----------------- + = pd max v s i smax v outi v s ? () i1 = n i loadi + = el5152, el5153, el5252, el5455
11 fn7385.4 october 3, 2005 application circuits sullen key low pass filter a common and easy to implemen t filter taking advantage of the wide bandwidth, low offset and low power demands of the el5152. a derivation of th e transfer function is provided for convenience. (see figure 28.) sullen key high pass filter again this useful filter benefits from the characteristics of the el5152. the transfer function is very similar to the low pass so only the results are presented. (see figure 29.) figure 28. sullen key low pass filter k 3 1 q rc 1 wo k holp c r c r c r c r c r c r ) k 1 ( 1 q c r c r 1 wo k holp ) c r c r c r ) k 1 (( jw c r c r w 1 1 ) jw ( h 1 s ) c r c r c r ) k 1 (( s c r c r k ) s ( h 0 s c 1 vi vo r v k vo 1 r vi v v 1 s c r 1 k vo r r 1 k 1 1 2 2 1 2 2 1 2 2 1 1 2 2 1 1 2 2 2 1 1 1 2 2 1 1 2 2 21 2 1 1 1 2 2 2 1 1 1 2 1 1 1 1 2 2 a b ? = = = + + ? = = = + + ? + ? = + + + ? + = = ? + ? + ? + = + = equations simplify if we let all components be equal r=c + - 1n 5v v2 c1 r1 r2 v1 1k c2 ra 1k 1k rb 5v v3 r7 1k v out 1 3 2 v+ v- 4 u1a 1n 1n 1k 11 l1 10h c6 1n c3 r5 1k 1n c5 l3 10h 1n c4 r6 1k el5152, el5153, el5252, el5455
12 fn7385.4 october 3, 2005 differential output instrumentation amplifier the addition of a third amplifier to the conventional three amplifier instrumentation amplif ier introduces the benefits of differential signal realization, specifically the advantage of using common mode rejection to remove coupled noise and ground-potential errors inherent in remote transmission. this configuration also provides enhanced bandwidth, wider output swing and faster slew rate than conventional three amplifier solutions with only the cost of an additional amplifier and few resistors. figure 29. sullen key high pass filter k 4 2 q rc 2 wo k 4 k holp c r c r c r c r c r c r ) k 1 ( 1 q c r c r 1 wo k holp 1 1 2 2 1 2 2 1 2 2 1 1 2 2 1 1 ? = = ? = + + ? = = = equations simplify if we let all components be equal r=c + - 1n 5v v2 c9 r8 v1 1k c2 ra 1k 1k rb 5v v3 r7 1k v out 1 3 2 v+ v- 4 u1a 1n 1n 11 l1 10h c6 1n c3 r5 1k 1n c5 l3 10h 1n c4 r6 1k c7 1n + - - + - + + - e o e o 4 e o 3 ref r 3 r 3 r 3 r 3 r 3 r 3 r 2 r 2 r g a 2 e 2 a 4 a 3 r 3 r 3 a 1 e 1 + - e o3 12r 2 r g ? + () e 1 e 2 ? () ? = e o4 12r 2 r g ? + () e 1 e 2 ? () = e o 21 2r 2 r g ? + () e 1 e 2 ? () ? = bw 2f c1 2 , a di ----------------- - = a di 21 2r 2 r g ? + () ? = el5152, el5153, el5252, el5455
13 fn7385.4 october 3, 2005 strain gauge the strain gauge is an ideal application to take advantage of the moderate bandwidth and hi gh accuracy of the el5152. the operation of the circuit is ve ry straight forward. as the strain variable component resistor in the balanced bridge is subjected to increasing stra in its resistance changes resulting in an imbalance in the bridge. a voltage variation from the referenced high accuracy source is generated and translated to the difference amplifier through the buffer stage. this voltage difference as a function of the strain is converted into an output voltage. + - 5v v2 22 r17 1k 1k rf 5v v4 rl 1k v out (v1+v2+v3+v4) 1 3 2 v+ v- 4 u1a 22 11 r18 1k 1k r15 v5 1k 0v variable subject to strain r16 1k r14 4 4 1n l4 10h c6 1n c3 r5 1k 1k 1n c12 1n c11 r11 1k l1 10h el5152, el5153, el5252, el5455
14 fn7385.4 october 3, 2005 msop package outline drawing el5152, el5153, el5252, el5455
15 fn7385.4 october 3, 2005 so package outline drawing el5152, el5153, el5252, el5455
16 all intersil u.s. products are manufactured, asse mbled and tested utilizing iso9000 quality systems. intersil corporation?s quality certifications ca n be viewed at www.intersil.com/design/quality intersil products are sold by description only. intersil corpor ation reserves the right to make changes in circuit design, soft ware and/or specifications at any time without notice. accordingly, the reader is cautioned to verify that data sheets are current before placing orders. information furnishe d by intersil is believed to be accurate and reliable. however, no responsibility is assumed by intersil or its subsidiaries for its use; nor for any infringements of paten ts or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of intersil or its subsidiari es. for information regarding intersil corporation and its products, see www.intersil.com fn7385.4 october 3, 2005 sot-23 package outline drawing note: the package drawing shown here may not be the latest version. to check the latest revision, please refer to the intersil w ebsite at http://www.intersil.com/design/packages/index.asp el5152, el5153, el5252, el5455

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